November 1946 RadioCraft
[Table of Contents]
Wax nostalgic about and learn from the history of early electronics.
See articles from RadioCraft,
published 1929  1953. All copyrights are hereby acknowledged.

This very extensive article
on ironcore inductors appeared in the November 1946 issue of RadioCraft
magazine. The first part, published the month prior in October, was an introductions
to terms of inductance and magnetism, while this one deals with actual design curves
and formulas. Iron core and air core inductors are the focus, and as you might guess
(due to the use of iron cores) the frequency range addressed is audio and relatively
low intermediate frequency (IF). In fact, separate treatment is given to coils operating
at DC (direct current) and AC (alternating current). Back in the day, not only were
most of the components inside a radio, television, record player, or other types
of electronics devices serviceable (i.e., replaceable), but the components themselves
were considered serviceable. That is, inductors, speaker coils, transformers, and
even some capacitors were often repaired or modified to fix nonworking circuits
or to improve marginally functioning ones.
Coils, Cores and Magnets  Part II  Reactor and Transformer Measurement and
Design
IronCore Inductance Design Nomograph
By H. W. Schendel
Filter chokes or reactors, audiofrequency chokes, and audio transformers come
under the classification of ironcore inductances. The unit of inductance is the
henry. A coil has an inductance of one henry if a current changing at the rate of
one ampere in one second induces one volt in it.
Basically inductances are the same as electromagnets and use cores like the relays
described in the first part of this article. The essential difference is that inductance
is the main consideration. This in turn depends on the permeability of the steel
or alloy.
Considerable care is required in rewinding good grade audio devices but it is
a comparatively simple matter to rewind filter chokes and obtain approximate original
characteristics. If a unit is rewound with original size wire, with about the same
number of turns, and close attention given the size of air gap, if any, no trouble
should be encountered. When an air gap has been used its size is extremely important.
In some cases a change of 0.001 inch in air gap total length will cause a 50 percent
change in final inductance. Generally speaking it is better to err slightly oversize
rather than undersize.
Much valuable information on rewinding, including a copper wire table,
appeared in articles in the August, September, October, and December 1942, and the September 1943
issues of RadioCraft.
To rewind an ironcore inductance for other than original conditions or to design
one for some specific purpose involves several factors.
Fig. 4 & Fig. 5  Inductance measurement configurations.
Inductance Formulas  Symbols and equivalent English and C.G.S.
units of common magnetic terms and formulas.
Windings of ironcore coils carrying only a.c. have an inductance which varies
in relation to the induced flux in a manner similar to the variation of the d.c.
permeability obtained from Fig. 1, which appeared last month. Pushpull output transformers
in which the d.c. effects cancel and inter stage transformers which have the d.c.
blocked from their windings are examples of the simple a.c, class.
Most ironcore inductance windings carry both a.c. and d.c. simultaneously 
a.c. superimposed on d.c. As either of these may be varied in magnitude it is easy
to see there would be an almost endless number of conditions, each resulting in
a different inductance. The inductance rating of any device is accurate only when
the test conditions are the same as the normal load conditions.
Curves may be prepared showing the a.c. flux density (B_{maxac}) versus
a.c. permeability (μ_{ac}) for various values of d.c. in the winding.
Such curves prepared from test data on a special test core are called incremental
permeability curves.
Due to the factors explained in connection with d.c. magnetization curves as
well as other factors  eddycurrent insulation, stacking factors, core shapes and
sizes, and other characteristics of laminations  separate permeability curves are
needed for each core design. The curves, when prepared from data obtained directly
from a definite working design, using a specified steel or alloy, are called apparent
permeability curves (μ_{a}). They indicate the actual permeability (not
theoretical) which the design appears to have under selected working conditions.
An air gap is seldom used when the inductance is used only on a.c. except in
such devices as fluorescent lamp and sunlamp ballasts. Lamp ballast design must
permit sufficient current to flow through the ballast for normal operation, make
available enough starting voltage, yet limit the current to a safe value at all
times.
Most inductances having d.c. in the windings have an air gap in the magnetic
circuit. This is to increase the apparent permeability over that available without
an air gap. The length of air gap which results in highest permeability and likewise
highest inductance for the particular current conditions in the windings is called
the optimum air gap.
Optimum air gap may be computed by proper application of the normal d.c. magnetization
curve and the incremental permeability curve for a given steel and core. The procedure
is rather lengthy and will not be presented here. The average experimenter would
probably find it faster to use a test circuit and obtain apparent inductance, apparent
permeability, and optimum air gap simultaneously.
Circuits suitable for measuring inductance, determining apparent permeability
and optimum air gap, are shown in Figs. 4 and 5. The Fig. 4 circuit is suitable
for low and zero direct current. D.c. saturation of the transformer core is eliminated
with the Fig. 5 circuit but the circuit has the disadvantage of requiring two similar
chokes.
In either circuit the d.c. is first adjusted to the normal working condition.
R4 and R5, Fig. 5, must be so adjusted that no d.c. flows through R3. This can be
determined by a d.c. v.t. voltmeter across R3. Sufficient a.c. voltage is applied
to give the working values across L1, as measured by an a.c. v.t. voltmeter. Connecting
it across R3 will give the voltage drop due to the a.c. flowing through L1.
The optimum air gap may now be found by varying the gap length until the a.c.
voltage across R3 reaches a minimum with the a.c. voltage and direct current across
L1 held to the working values. For Fig. 5 the air gaps must be the same for L1 and
L2 and both varied simultaneously.
Inductance Formulas
The apparent inductance of L1 in henries will be
where R3 = d.c. resistance of voltmeter shunt in ohms, E_{L} = a.c. volts
across L1, E_{R} = a.c. volts across R3, f =a.c. test frequency, and R_{a}
=apparent resistance of L1. (R_{a} consists of the d.c. resistance plus
resistance effects due to core losses. The latter are very low in goodgrade laminated
cores.) Usually R_{a} is small compared to the inductive reactance of the
coil and could be omitted, simplifying the formula to
L_{a} = 0.159 R_{3} E_{L}) / f E_{R}
Because L1 and L2, Fig. 5, are in parallel, L_{a} must be multiplied
by 2 to obtain the value for L1.
Knowing L_{a}, the apparent permeability can be found to be
μ_{a} = (10^{8} 1 L_{a}) / (3.19
N^{2 }A K_{1})
where 1 length of core in inches, A = area ,of core in square inches, N = number
of turns in coil, and K_{1} = stacking factor (usually about 0.9).
The a.c. flux density in lines per square inch will be
B_{ac} = (10^{8} E_{rms}) / 4.44 f N
A K_{1}
where E_{rms} = a.c. voltage across L1 and other symbols as before.
To simplify calculations for average cores an IronCore Inductance Design Chart
has been constructed in Fig. 6. The symbols at the scale headings may be identified
from the previous text. The multiplying scales X_{1} X_{2}, X_{3}
are used to obtain readings.
The Inductance Design Chart is constructed to automatically allow a 0.9 lamination
stacking factor. O_{dc} points, and the B_{ac} and TC_{a}
turning curves were prepared from data on 29 gauge (0.014inch) steel laminations
having properties similar to those on Curve 1, Fig. 1, which appeared last month.
These properties were taken as an average. Some steels will give more inductance,
others less. Now points and turning curves may be constructed for steels and cores
with other characteristics. The balance of the chart would remain unchanged.
The previous B_{ac} formula may be used to assist in selecting one of
the B_{ac} turning curves or O_{dc} points on the chart.
Values of B_{ac} may be less than 65 for some interstage a.f. transformers
and smoothing chokes while for some output transformers and swinging or input chokes
it may go well beyond 3500. Turning curve TC_{a} is used to obtain air gap
length for all values of B_{ac}.
Use of the Chart
Assume we have a core like Fig. 3 (last month's issue) to be used for a smoothing
choke. The core is 1 inch wide and stacked 1 inch high using 29 gauge (.014inch)
steel laminations, making the area (A) = 1.0 square inch. The entire core has uniform
crosssectional area (each of the two outer legs have onehalf the area of the center
leg). The core length (average length around each window as indicated in Fig.
3) l_{s} = 6.0 inches. Window is 1/2 x 1/2 inch. B_{ac} = 650 will
be satisfactory and there will be 80 ma d.c. in the windings. The problem is to
find the maximum inductance, L_{a} in henries, and the optimum air gap,
l_{a}, in inches.
The more turns the greater the inductance but wire size, allowable resistance
and window area will limit the number. Wire size and coil dissipation watts may
be computed as outlined for electromagnets. If the coil resistance is too great
larger wire may be used.
A fairly reliable method is to select a wire, allowing 750 to 1250 circular mils
per ampere. A wire table and a few computations will show that 3500 turns, No. 32
enamel wire, would go in the window and have a resistance of about 250 ohms.
This information may now be applied to the Inductance Design Chart, Fig. 6. The
column headed "Order of Scales" indicates the function of certain groups of scales
and under each function is given the order in which the scales are read at each
setting of a straightedge. Mistakes will be prevented by writing down the reading
for each scale.
Using the group of scales "FOR D.C." set a straightedge from 3500 (no. of turns)
on N to "80 (no. of milliamperes) on M.A. and read 3.23 on X_{1}; From 3.23
on X_{1}, to 6 (lgth. of core, inches) on l_{s} and read 4.02 on
X_{2}; Next from 6 (core length) on l_{s} to 1 (core area, sq. in.)
on A and read 8.78 on X_{1}; From the 8.78 on X_{1} to 3500 (no.
of turns) on N and read 7.38 on X_{3}; From 4.02 previously obtained on
X_{2} over the B_{ac} = 650 curve and read 222 on μ_{a};
From 222 on μ_{a} to 7.38 previously obtained on X_{3} and read
13 on L_{a}, the apparent inductance in henries.
The optimum air gap may be found by using the "AIR GAP" group of scales. From
4.02 found above for X_{2} over the point of the TC_{a} curve read
170 on μ_{a}; From 170 on μ_{a} to 6 (core length) on l_{s}
and read 0.0153 on l_{a}, the total length of the air gap, in inches. (See
Fig. 3.)
Although not a part of the problem let us suppose there is .no d.c. in the windings.
What will be the inductance? For this we use the "NO D.C." group of scales. To proceed
set a straightedge from 6 (length of core) on l_{s} to 1 (area of core)
on A and read 8.78 on X_{1}; From 8.78 on X_{1} to 3500 (no. of
turns) on N read 7.38 on X_{3}; From 7.38 on X_{3} to O_{dc}
/ (B_{ac} = 65) point on μ_{a} and read 37 on L_{a},
the apparent inductance in henries. If B_{ac} is nearer 650 than 65, the
L_{a} would be over 60 henries. No air gap would be used. Instead, the laminations
would be interleaved as on any transformer.
Transformers, Swinging Chokes
Audio frequency and output transformers are designed mainly on the basis of inductance
of the primary winding, making the design problems similar to chokes except that
secondary windings follow regular transformer procedure for impedance and turns
ratios needed. Inductance values range from 2 to 50 henries and more, the higher
inductance values giving better low frequency response, especially when used with
tubes having high plate resistance.
Swinging chokes are often desirable when the load varies widely. The main difference
between a swinging and smoothing choke is that the former, though designed for high
d.c., has a shorter than optimum air gap. This shortened air gap lowers the inductance
considerably at high d.c. loads and increases it at low d.c. loads when compared
to a choke designed for high d.c. only.
The Fig. 6 chart is useful only for rough design of a swinging choke. Select
the wire for the maximum d.c. ma and assume some value for turns to fit on the core.
From the chart determine L_{a} at maximum d.c. and multiply the value found
by 0.58 for the actual minimum swinging choke inductance. If this figure proves
to be unsuitable try again using new values for turns or core.
After suitable values have been found for the maximum d.c. use all of them except
that in place of the maximum d.c. ma substitute a value only 10 percent of the
maximum d.c. ma and find the length of optimum air gap from the chart. Multiply
the length as found by 2.6 to find the total air gap length to use for the swinging
choke. Inductance ratio between maximum and 10 percent of maximum d.c. will be about
4 to 1. A shorter air gap would increase the ratio but would decrease the inductance
at maximum d.c.
A handy reference chart of conversion factors and formulas (see page 27) shows
some unusual variations. Unidentified symbols are explained in the text.
Acknowledgement is given Allegheny Ludlum Steel Corporation, United States Steel
Corporation, and American Rolling Mill Company for information on electrical steels.
Posted February 7, 2022
