Scattered Thoughts on Scattering Parameters
Sunshine Design Engineering Services
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on Scattering Parameters By Joseph L. Cahak
2013 Sunshine Design Engineering Services
Scattering parameters or S-parameters
(aka Spars) are used by RF and microwave engineers to measure and design components and systems
at those frequency ranges. These S-parameters are typically measured with an instrument called
a vector network analyzer, or VNA.
Complex Numbers and Parameters
A complex number is represented by two values X and Y, as in X + iY = Z.
X is the real component and iY is the imaginary component with Z being the complex representation.
The letter ‘i’ is used to designate the complex operator (√-1) by scientists and mathematicians,
but in engineering the letter ‘j’ is most often used. This is used to represent AC or RF signals.
X may be the resistance and Y the reactance in ohms of the component to an AC signal. A standard
RF load for instance is represented by 50 ohms real resistance and some reactance with good
loads having reactance close to 0 ohms. X + iY can also represent a voltage and current
as a function of time. Current is a function of the load and the voltage applied, so the resistances,
voltages and currents are all important in describing a network for DC and AC (or RF) signals.
A 2-port network can be represented by two equations with four parameters. The four parameters
have different representations depending on what is known and what operations the users desire
to use them for. Some network parameters (ABDC, S-, Z-, Y-, h-, etc.) are better than others
depending on circuit types and the operations on them.
Open circuit impedance parameters are used to represent the impedances of the network.
The values are complex and represent real resistance (R) and reactance (jX) of the elements
of the network.
Short circuit parameters or admittance parameters are
used to represent the inverse of impedance. The real and imaginary parts are conductance (G)
and susceptance (jB). The units are mhos or Siemens.
Another model commonly used to analyze BJT (bipolar junction transistor) circuits is the
h-parameter model, closely related to the hybrid-pi model and the y-parameter two-port model,
but the h-parameter model uses input current and output voltage as independent variables, rather
than input and output voltages. In this case it is a hybrid of an open circuit on the input
and a short circuit on the output.
Often this circuit is selected when a voltage amplifier is wanted at the output. The off-diagonal
g-parameters are dimensionless, while diagonal members have dimensions the reciprocal of one
ABCD or T Parameters
ABCD-parameters are known variously as chain, cascade,
or transmission line parameters. This is useful for cascading 2 port network responses.
ABCD’ or T’ Parameters
These are the inverse of the ABCD or T-parameters,
respectively. They are useful for de-embedding 2-port network responses when multiplied with
the ABCD matrix for the overall network.
There are matrix transforms that are used to
convert from one network description to another. Typically the S, Z, Y, h and ABCD are direct
conversions. The conversion to a few of the others are after the base conversion and then converting
from h to the inverse g for instance, ABCD with the inverse ABCD-1 and S-parameter to
the T (one of the two types) or the anti-S parameter (S-1) . Note that the ABCD matrix
is also known as a “T” matrix; this is not to be confused with the other two descriptions of
a “T” matrix connected with the S-parameters calculations and will be presented in another paper.
See Figure 1 for a graphical representation of the transformations available.
Figure 1 - Network Description Transformations
Some of the transmission line functions and parameters are complex in value. They are excited
by RF signals with most having complex modulation applied to them. Some basic measurement parameters
need to be defined. A load can be represented at RF frequencies as a real resistance and an
imaginary reactance driven by the charge delay or advancement as related to the driving voltage.
This complex impedance is written as Z(ohms) = X + iY, with Z being complex
value of the real (X) and imaginary (Y) components. Y is positive for an inductive element and
negative for a capacitive element.
When a RF signal
is incident to a load, some of the signal is absorbed and converted to heat and radiated, what
isn’t absorbed is reflected back to the source as shown in Figure 2 and 3. Reflection coefficient
represents this value in power measurements and is also known as rho or
ρ = Γ = |Power Reflected/Power Incident|.
Rho can be converted to the voltage standing wave ratio, or VSWR, by the equation VSWR = (1+ρ)/(1-ρ).
These measurements are still scalar, but dimensionless. Rho and VSWR are measured in units of
power (single dimension), but the ratio cancels the units out (thus dimensionless). Rho and
VSWR can also be derived by the system impedances. The load can be represented by Z = R
+jX. The measurement system used to characterize a component or another system also has impedance.
This measurement with the device or network sets up an impedance match represented by gamma
or Γ = (Zsys-Z)/(Zsys+Z) = (Power Reflected)/(Power Incident).
The gamma, or complex reflection coefficient, can be transformed by absolute value to rho, or
, which can be used to derive the VSWR as given above. It can also be transformed by the system
impedance to the load impedance.
Figure 2 – S11 or Gamma Source Signal Flow
Figure 3 - Power Reflected
When a signal is incident to a 2-port network, the
network looks like a load to the source, but the network has an output and a match at the output.
The device has reflections from the output back to the input in addition to the transmitted
part of the incident signal. As with the Reflection case, there is also some energy absorbed
and converted to heat. The transmitted signal can be represented by Tau or
τ = (Power Transmitted)/(Power Incident).
See Figures 4 and 5.
Figure 4 - Transmission Network Signal Flow
Figure 5 - Transmitted
Units of Measurement
Resistance is measured in ohms, voltage
in volts, current in amps. Power is measured in watts. This can be referenced to a specific
power level. Tradition and convention stipulate 1mW as 0 dBm. With this power can be represented
in logarithmic units or decibels, dB for relative power gain or loss and dBm for absolute power
level referenced to 1 mW. When power is measured the type of measurement makes a difference
in how the units are converted. A Power Meter measures in Volt-Amps or true power as opposed
to reactive or apparent power. The formula to convert real power to decibels is
dB = 10*log10 [(Power Out)/(Power In)].
To convert measurements made in voltages, not true power, and this includes vector network
analyzers, vector signal analyzers and spectrum Analyzers use the formula
dB = 20*log10 [(Voltage Out)/(Voltage In)].
This can be derived from the fact that Power = Voltage2/Resistance
, thus the doubling of the multiplier of the logarithm of the voltage ratio measurement of power.
Convert dB to Watts using the inverse formulas:
Watts = 10Power/10 and
The absolute power can be converted between Watts and dBm with the
Watts =10 (dBm/10) - 3 and dBm = 10*log10
dB units is a relative or ratio measurement. For power measurements adopted
convention is to measure the signal relative to 1 mWatt for dBm and 1 V for dBV.
S-parameters a and b components are in units
of power represented as the square root of the power or
Power Incident at Port 1 or
a1 = V1+/√Zo
at Port 2 or a2 = V2+/√Zo
Power Emitted at Port 1 or b1 = V1-/√Zo
Power Emitted at Port 2 or b1 = V2-/√Zo
b1 = S11a1 + S12a2
b2 = S21a1 + S22a2
Figure 6 - 2-Port S-Parameter Signal Flow
Figure 6 shows the signal flow diagram for
the S-Parameters. Note that the dimension of a1,a2 and b1,b2
are complex. These can then be used to derive the Scattering Parameters (Spars) for the network
which are also complex values and dimensionless due to the ratio and in the case below are in
rectangular coordinates and have linear magnitudes, not dB. Note that S-Parameters are dependent
on the system Impedance. S-Parameters at one system impedance are not equal to S-Parameters
at another System Impedance.
S11 = b1/a1 or
forward reflection coefficient
S12 = b1/a2 or
reverse transmission coefficient
S21 = b2/a1 or
forward transmission coefficient
S22 = b2/a2 or
reverse reflection coefficient
Note also that the reflection coefficient for the
load and source, ΓL = b2/a2 and
Γs = b1/a1
, respectively are the same as S22 = b2/a2 and
S11 = b1/a1 . In other words, if you measure
the 1 port S-Parameter of a source or load, it is the same as the Gamma or
Γ . These S-parameters
are the basis of many RF and Microwave measurements.
Network Analyzer Measurements
In many RF and Microwave measurements the S-Parameters are typically expressed in dB (decibels)
Magnitude units and Degrees in the polar coordinate system. Network and Vector Network Analyzers
and Spectrum Analyzers all measure with voltage ratio measurements, so to convert to dB in terms
of volts we must use the following equation.
dB = 20*log10 [(Voltage Out)/(Voltage In)]
Making measurements of S-parameters is a process of measurements made with calibrations standards
(special components with values traceable to NIST or other designated agencies) and formulas
to compute the correction factors from the measurement of those standards that determine a reference
plane for the measurements. The measurement reference plane is an imaginary plane of reference
for the measurements being made that lies somewhere between the measurement system’s output
and input ports, inclusive. It defines the points to which the network analyzer is calibrated
to have 0 dB magnitude and 0 degrees phase response. It is the input and output planes
to which reflection and transmission measurements are referenced. Another aspect of the relative
measurement is that within the VNA dynamic range, the input power can be varied and the network
response will stay the same until the power level goes outside the dynamic range.
There are numerous methods and standards for coaxial, waveguide, planar, probe and other interconnections
methods. There are also a number of test fixtures available and calibration techniques to help
the test engineer make measurement in fixtures and give them the ability to de-embed fixture
components to get at the raw device or subsystem S-parameters, which are difficult or nearly
impossible to measure with standard equipment (e.g. mixed impedances).
I recently attended the Agilent “Back to Basics” seminar and as with the first one I attended
20 years ago, they still cover all the basics of measurements, S-parameters, measurement
systems and how to use them. The new instruments all have the extended measurement capabilities
built in with some really exciting capabilities. Spectrum analyzers can now reach down into
the noise floor “Noise Floor Extension” and get to -172 dBm/Hz. This is a mere 2 dB
from the theoretical noise limit at room temperature (recall that 25°C gives a 50 ohm noise
power of -174 dBm in a 1 Hz bandwidth).
The new oscilloscopes have some amazing
features across the board and at lower costs. They have very high bit depth and are being used
for the spectrum analyzer and vector signal analyzers (VSA) front ends, as they have in some
cases more than 14 bits of ADC depth, thereby giving much greater dynamic range. Finally the
exciting news on the vector network analyzer (VNA) measurement front is the new X-parameter
test sets that can do large signal multi-harmonic, power and spurious analysis, in addition
to the small signal S-parameters. This is important because now the non-linear characteristics
of device and circuit response can be measured in addition to the linear characteristics. With
this new information much more accurate device and circuit models can be formulated, yielding
a more accurate model for designers to use in simulations.
We showed that S-parameters can be used for a number of network computations that can add
value to measurements where the equipment is limited in features. The reader can find these
equations and more in my S-Parameter Library (DLL & LLB) and my RF Calculator products.
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Posted August 1, 2013